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EL5152, EL5153, EL5252, EL5455
Data Sheet October 3, 2005 FN7385.4
270MHz Ultra-Accurate Amplifiers
The EL5152, EL5153, EL5252, and EL5455 are 270MHz bandwidth -3dB voltage mode feedback amplifiers with DC accuracy of <0.01%, 1mV offsets and 50kV/V open loop gains. These amplifiers are ideally suited for applications ranging from precision measurement instrumentation to high-speed video and monitor applications demanding higher linearity at higher frequency. Capable of operating with as little as 3.0mA of current from a single supply ranging from 5V to 12V dual supplies ranging from 2.5V to 5.0V these amplifiers are also well suited for handheld, portable and battery-powered equipment. Single amplifiers are offered in SOT-23 packages and duals in a 10 Ld MSOP package for applications where board space is critical. Quad amplifiers are available in a 14 Ld SO package. Additionally, singles and duals are available in the industry-standard 8 Ld SO. All parts operate over the industrial temperature range of -40C to +85C.
Features
* 270MHz -3dB bandwidth * 180V/s slew rate * 1mV maximum VOS * Very high open loop gains 50kV/V * Low supply current = 3mA * 105mA output current * Single supplies from 5V to 12V * Dual supplies from 2.5V to 5V * Fast disable on the EL5152 and EL5252 * Low cost * Pb-Free plus anneal available (RoHS compliant)
Applications
* Imaging * Instrumentation * Video * Communications devices
Pinouts
EL5152 (8 LD SO) TOP VIEW
NC 1 IN- 2 IN+ 3 VS- 4 + 8 CE 7 VS+ 6 OUT 5 NC
EL5153 (5 LD SOT-23) TOP VIEW
OUT 1 VS- 2 IN+ 3 +4 IN5 VS+
EL5252 (10 LD MSOP) TOP VIEW
INA+ 1 CEA 2 VS- 3 CEB 4 INB+ 5 + + 10 INA9 OUTA 8 VS+ 7 OUTB 6 INB-
EL5455 (14 LD SO) TOP VIEW
OUTA 1 INA- 2 INA+ 3 VS+ 4 INB+ 5 INB- 6 OUTB 7 -+ +-+ +14 OUTD 13 IND12 IND+ 11 VS10 INC+ 9 INC8 OUTC
1
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 1-888-468-3774 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright Intersil Americas Inc. 2004, 2005. All Rights Reserved All other trademarks mentioned are the property of their respective owners.
EL5152, EL5153, EL5252, EL5455 Ordering Information
PART NUMBER EL5152IS EL5152IS-T7 EL5152IS-T13 EL5152ISZ (See Note) EL5152ISZ-T7 (See Note) EL5152ISZ-T13 (See Note) EL5153IW-T7 EL5153IW-T7A EL5153IWZ-T7 (See Note) EL5153IWZ-T7A (See Note) EL5252IY EL5252IY-T7 EL5252IY-T13 EL5455IS EL5455IS-T7 EL5455IS-T13 EL5455ISZ (See Note) EL5455ISZ-T7 (See Note) EL5455ISZ-T13 (See Note) PART MARKING 5152IS 5152IS 5152IS 5152ISZ 5152ISZ 5152ISZ BGAA BGAA TAPE & REEL 7" 13" 7" 13" 7" (3K pcs) 7" (250 pcs) 7" (3K pcs) 7" (250 pcs) 7" 13" 7" 13" 7" 13" 8 Ld SO 8 Ld SO 8 Ld SO 8 Ld SO (Pb-free) 8 Ld SO (Pb-free) 8 Ld SO (Pb-free) 5 Ld SOT-23 5 Ld SOT-23 5 Ld SOT-23 (Pb-free) 5 Ld SOT-23 (Pb-free) 10 Ld MSOP 10 Ld MSOP 10 Ld MSOP 14 Ld SO 14 Ld SO 14 Ld SO 14 Ld SO (Pb-free) 14 Ld SO (Pb-free) 14 Ld SO (Pb-free) PACKAGE PKG. DWG. # MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0038 MDP0038 MDP0038 MDP0038 MDP0043 MDP0043 MDP0043 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027 MDP0027
BAAL BAAL
BAGAA BAGAA BAGAA 5455IS 5455IS 5455IS 5455ISZ 5455ISZ 5455ISZ
NOTE: Intersil Pb-free plus anneal products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020.
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455
Absolute Maximum Ratings (TA = 25C)
Supply Voltage between VS and GND. . . . . . . . . . . . . . . . . . . 13.2V Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA Pin Voltages . . . . . . . . . . . . . . . . . . . . . . . . . GND -0.5V to VS +0.5V Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +125C Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65C to +150C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40C to +85C Current into IN+, IN-, CE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5mA
CAUTION: Stresses above those listed in "Absolute Maximum Ratings" may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA
Electrical Specifications
PARAMETER AC PERFORMANCE BW -3dB Bandwidth
VS+ = +5V, VS- = 5V, RF = RG = 750, RL = 150, TA = 25C, unless otherwise specified. CONDITIONS MIN TYP MAX UNIT
DESCRIPTION
AV = +1, RL = 500, CL = 5.0pF AV = +2, RL = 150
270 85 165 50 120 155 180 30 0.06 0.045 12 1.8
MHz MHz MHz MHz V/s V/s ns % nV/Hz pA/Hz
GBWP BW1 SR
Gain Bandwidth Product 0.1dB Bandwidth Slew Rate
RL = 150 AV = +1, RL = 500 VO = -3V to +3V, AV = +2 VO = -3V to +3V, AV = 1, RL = 500
tS dG dP VN IN
0.1% Settling Time Differential Gain Error Differential Phase Error Input Referred Voltage Noise Input Referred Current Noise
VOUT = -1V to +1V, AV = +2 AV = +2, RL = 150 AV = +2, RL = 150
DC PERFORMANCE VOS TCVOS AVOL Offset Voltage Input Offset Voltage Temperature Coefficient Open Loop Gain Measured from TMIN to TMAX VO is from -2.5V to 2.5V (EL5152 & EL5153) VO is from -2.5V to 2.5V (EL5252 & EL5455) INPUT CHARACTERISTICS CMIR CMRR IB IOS RIN CIN Common Mode Input Range Common Mode Rejection Ratio Bias Current Input Offset Current Input Resistance Input Capacitance Guaranteed by CMRR test VCM = 2.5 to -2.5 -2.5 85 -0.4 -80 25 110 0.12 12 60 1 +0.6 80 2.5 V dB A nA M pF 10 15 -1 0.5 -2 20 50 1 mV V/C kV/V kV/V
OUTPUT CHARACTERISTICS VOUT Output Voltage Swing RL = 150 to GND RL = 500 to GND IOUT Output Current RL = 10 to GND 3.0 3.4 60 3.3 3.7 105 V V mA
ENABLE (SELECTED PACKAGES ONLY) tEN tDIS Enable Time Disable Time 200 300 ns ns
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EL5152, EL5153, EL5252, EL5455
Electrical Specifications
PARAMETER IIHCE IILCE VIHCE VILCE SUPPLY ISON ISOFF PSRR Supply Current - Enabled (per amplifier) No load, VIN = 0V, CE = +5V 2.46 5 85 80 3.0 13 116 95 3.43 25 mA A dB dB VS+ = +5V, VS- = 5V, RF = RG = 750, RL = 150, TA = 25C, unless otherwise specified. (Continued) CONDITIONS CE = VS+ CE = VS5 VS+ -1 VS+ -3 MIN TYP 0 13 MAX -1 25 UNIT A A V V
DESCRIPTION CE Pin Input High Current CE Pin Input Low Current CE Input High Voltage for Power-down CE Input Low Voltage for Power-up
Supply Current - Disabled (per amplifier) No load, VIN = 0V, CE = 5V Power Supply Rejection Ratio DC, VS = 3.0V to 6.0V (EL5152 & EL5153) DC, VS = 3.0V to 6.0V (EL5252 & EL5455)
Typical Performance Curves
90 60 30 PHASE () AV=+1 AV=+2 AV=+5 0 -30 -60 -90 -120 -150 -180 100M 500M Supply=5.0V INPUT=-30dBm=20mV RL=500 CL=5pF 1M 10M FREQUENCY (Hz) 100M 500M AV=+5 AV=+2 AV=+1
4 NORMALIZED GAIN (dB) 3 2 1 0 -1 -2 -3 Supply=5.0V -4 INPUT=-30dBm=20mV RL=500 -5 C =5pF L -6 100K 1M 10M FREQUENCY (Hz)
-210 100K
FIGURE 1. EL5152 SMALL SIGNAL FREQUENCY FOR VARIOUS GAINS
FIGURE 2. EL5152 SMALL SIGNAL FREQUENCY PHASE FOR VARIOUS GAINS
5 NORMALIZED GAIN (dB) 4 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 10M FREQUENCY (Hz) CL=5pF AV=+1
10 NORMALIZED GAIN (dB)
5 4 3 2 1 0 -1 -2 -3 -4
AV=+1 RL=500
12pF 10pF 4.7pF 3.3pF
50 500 150
2.2pF 1pF What should label be fore this curve? 1M 10M FREQUENCY (Hz) 100M 500M
100M
500M
-5 100K
FIGURE 3. FREQUENCY RESPONSE FOR VARIOUS RL
FIGURE 4. FREQUENCY RESPONSE FOR VARIOUS CL
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455 Typical Performance Curves
4 NORMALIZED GAIN (dB) 3 2 1 0 -1 -2 -3 -4 -5 -6 100K 1M 10M FREQUENCY (Hz) 100M 800M 250 500 NORMALIZED GAIN (dB) AV=+2 CL=5pF RF=500 50 100 200
(Continued)
5 4 3 2 1 0 -1 -2 -3 -4
AV=+2 RL=500 RF=500
22pF 18pF 12pF
4.7pF 2.7pF
-5 100K
1M
10M FREQUENCY (Hz)
100M
500M
FIGURE 5. FREQUENCY RESPONSE FOR VARIOUS RL
FIGURE 6. FREQUENCY RESPONSE FOR VARIOUS CL
4 NORMALIZED GAIN (dB) 3 2 1 0 -1 -2 -3 -4 -5
4 NORMALIZED GAIN (dB) AV=+5 CL=5pF RF=102 3 2 1 0 -1 -2 -3 -4 -5 1M 10M 100M -6 100K 1M 10M FREQUENCY (Hz) 100M 500M RL=500 AV=+5 RF=102 87pF 68pF 50pF 39pF 27pF 18pF
50 200
500 250
-6 100K
FREQUENCY (Hz)
FIGURE 7. FREQUENCY RESPONSE FOR VARIOUS RL
FIGURE 8. FREQUENCY RESPONSE FOR VARIOUS CL
5 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 4 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 10M FREQUENCY (Hz) 100M 500M RL=150 AV=+2 RF=500 4.7pF 3.3pF 3.2pF 1pF
5 4 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 10M FREQUENCY (Hz) 100M 500M RL=500 CL=5pF AV=+2 RF=RG= 1500 1000 750 500
FIGURE 9. FREQUENCY RESPONSE FOR VARIOUS CIN
FIGURE 10. FREQUENCY RESPONSE vs RF/RG
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455 Typical Performance Curves
-5 -4 NORMALIZED GAIN (dB) -3 -2 -1 0 -1 -2 -3 -4 -5 100K 1M 10M FREQUENCY (Hz) 100M 300M 0pF 34pF 22pF NORMALIZED GAIN (dB) RL=500 AV=+5 RF=102
(Continued)
5 4 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 10M FREQUENCY (Hz) 100M 500M Supply=5.0V RL=500 AV=+2 RF=500 2.0V 3.0V 4.0V 5.0V
FIGURE 11. FREQUENCY RESPONSE FOR VARIOUS CIN
FIGURE 12. FREQUENCY RESPONSE FOR VARIOUS POWER SUPPLY
0 -10 -20 -30 -40 -50 -60 -70 -80 -90 -100 1K
-30 AV=+1 -40 -50 CMRR (dB) -60 -70 -80 -90 -100 -110 -120 -130 100 5.0 2.5 3.0
PSRR (dB)
10K
100K
1M
10M
100M
1K
10K
100K
1M
10M
100M
FREQUENCY (Hz)
FREQUENCY (Hz)
FIGURE 13. PSRR
FIGURE 14. CMRR FOR VARIOUS POWER SUPPLY VALUES
1000
AV=+1
OUTPUT IMPEDANCE ()
100 10 1 0.01 0.001
AV=+1 RL=500 CL=0 CH 1 CH 2
328ns DISABLE
1K 10K 100K 1M 10M 100M FREQUENCY (Hz)
216ns ENABLE
TIME (400ns/DIV)
FIGURE 15. OUTPUT IMPEDANCE
FIGURE 16. ENABLE/DISABLE RESPONSE
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455 Typical Performance Curves
(Continued)
VOLTAGE (500mV/DIV)
0V
VOLTAGE (500mV/DIV)
AV=+1 RL=500 CL=5pF
AV=+1 RL=500 CL=5pF
0V
TIME (4ns/DIV)
TIME (4ns/DIV)
FIGURE 17. RISE TIME - LARGE SIGNAL RESPONSE
FIGURE 18. FALL TIME - LARGE SIGNAL RESPONSE
VOLTAGE (100mV/DIV)
VOLTAGE (100mV/DIV)
AV=+1 RL=500 CL=5pF
AV=+1 RL=500 CL=5pF
0V
0V
TIME (2ns/DIV)
TIME (2ns/DIV)
FIGURE 19. RISE TIME - SMALL SIGNAL RESPONSE
FIGURE 20. FALL TIME - SMALL SIGNAL RESPONSE
90 80 60
GAIN (dB)
-45 0
PHASE ()
-10 -20 CROSSTALK (dB) AV=+1 RL-500 CL=0pF
70 50 40 30 20 10 0 -10 1K
10K
GAIN
-30 -40 -50 -60 -70 -80 -90
45 90 135 180 100M 500M
IN #2 OUT #1
PHASE
IN #1 OUT #2
100K
1M
10M
-100 100K
1M
10M FREQUENCY (Hz)
100M
1G
FREQUENCY (Hz)
FIGURE 21. EL5152 SMALL SIGNAL OPEN LOOP GAIN vs FREQUENCY INVERTING
FIGURE 22. EL5252 SMALL SIGNAL FREQUENCY vs CROSSTALK
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455 Typical Performance Curves
7 NORMALIZED GAIN (dB) SUPPLY CURRENT (mA) 6 5 4 3 2 1 0 1 1.5 2 2.5 3 3.5 AV=+2 RL=500 CL=5pF
(Continued)
4 3 2 1 0 -1 -2 -3 -4 -5 5
RL=500 CL=0pF 2.0V 3.0V 4.0V 5.0V
4
4.5
-6 100K
1M
10M FREQUENCY (Hz)
100M
800M
VOLTAGE (V)
FIGURE 23. SUPPLY CURRENT vs SUPPLY VOLTAGE
FIGURE 24. FREQUENCY RESPONSE FOR VARIOUS VOLTAGE SUPPLY LEVELS
5 NORMALIZED GAIN (dB) 4 3 2 1 0 -1 -2 -3 -4 -5 100K 1M 10M FREQUENCY (Hz) 100M 1G CHANNEL #1 CHANNEL #2 AV=+1 RL-500 CL=0pF
FIGURE 25. EL5252 SMALL SIGNAL FREQUENCY - CHANNEL TO CHANNEL
1.4 POWER DISSIPATION (W)
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD POWER DISSIPATION (W) SO14 JA=88C/W SO8 JA=110C/W MSOP8/10 JA=115C/W SOT23-5/6 JA=230C/W 50 75 85 100 125 150
1 0.9
JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD SO14 JA=120C/W SO8 JA=160C/W MSOP8/10 JA=206C/W
1.2 1.136W 1 909mW 0.9 0.8 870mW 0.6 0.4 435mW 0.2 0 0 25
0.8 833mW 0.7 0.6 625mW 0.5 486mW 0.4 0.3 391mW 0.2 SOT23-5/6 0.1 =256C/W JA 0 0 25 50
75 85 100
125
150
AMBIENT TEMPERATURE (C)
AMBIENT TEMPERATURE (C)
FIGURE 26. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
FIGURE 27. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455 EL5152 Product Description
The EL5152, EL5153, EL5252, and EL5455 are wide bandwidth, low power, low offset voltage feedback operational amplifiers capable of operating from a single or dual power supplies. This family of operational amplifiers are internally compensated for closed loop gain of +1 or greater. Connected in voltage follower mode, driving a 500 load members of this amplifier family demonstrate a -3dB bandwidth of about 270MHz. With the loading set to accommodate typical video application, 150 load and gain set to +2, bandwidth reduces to about 180MHz with a 600V/s slew rate. Power down pins on the EL5152 and EL5252 reduce the already low power demands of this amplifier family to 17A typical while the amplifier is disabled. position of the pole shifts in the frequency domain, the amplifier's phase margin is reduced and the amplifier becomes less stable. Peaking in the frequency domain and ringing in the time domain are symptomatic of this shift in pole location. So we want to keep the feedback resistor as small as possible. You may want to use a large feedback resistor for some reason; in this case to compensate the shift of the pole and maintain stability a small capacitor in the few Pico farad range in parallel with the feedback resistor is recommended. For the gains greater than unity, it has been determined a feedback resistance ranging from 500 to 750 provides optimal response.
Gain Bandwidth Product
The EL5156 and EL5157 families have a gain bandwidth product of 210MHz for a gain of +5. Bandwidth can be predicted by the following equation:
Gain x BW = GainBandwidthProduct
Input, Output and Supply Voltage Range
The EL5152 and EL5153 families have been designed to operate with supply voltage ranging from 5V to 12V. Supply voltages range from 2.5V to 5V for split supply operation. Of course split supply operation can easily be achieved using single supplies by splitting off half of the single supply with a simple voltage divider as illustrated in the application circuit section.
Video Performance
For good video performance, an amplifier is required to maintain the same output impedance and same frequency response as DC levels are changed at the output; this characteristic is widely referred to as "diffgain-diffphase". Many amplifiers have a difficult time with this especially while driving standard video loads of 150, as the output current has a natural tendency to change with DC level. The EL5152 dG and dP for these families is a respectable 0.006% and 0.04%, while driving 150 at a gain of 2. Driving high impedance loads would give a similar or better dG and dP performance as the current output demands placed on the amplifier lessen with increased load.
Input Common Mode Range
These amplifiers have an input common mode voltage ranging from 1.5V above the negative supply (VS- pin) to 1.5V below the positive supply (VS+ pin). If the input signal is driven beyond this range the output signal will exhibit distortion.
Maximum Output Swing & Load Resistance
The outputs of the EL5152 and EL5153 families maximum output swing ranges from -4V to 4V for VS = 5V with a load resistance of 500. Naturally, as the load resistance becomes lower, the output swing lowers accordingly; for instance, if the load resistor is 150, the output swing ranges from -3.5V to 3.5V. This response is a simple application of Ohms law indicating a lower value resistance results in greater current demands of the amplifier. Additionally, the load resistance affects the frequency response of this family as well as all operational amplifiers, as clearly indicated by the Gain vs Frequency for Various RL curves clearly indicate. In the case of the frequency response reduced bandwidth with decreasing load resistance is a function of load resistance in conjunction with the output zero response of the amplifier.
Driving Capacitive Loads
The EL5152 and EL5153 families can easily drive capacitive loads as demanding as 27pF in parallel with 500 while holding peaking to within 5dB of peaking at unity gain. Of course if less peaking is desired, a small series resistor (usually between 5 to 50) can be placed in series with the output to eliminate most peaking. However, there will be a small sacrifice of gain which can be recovered by simply adjusting the value of the gain resistor.
Driving Cables
Both ends of all cables must always be properly terminated; double termination is absolutely necessary for reflection-free performance. Additionally, a back-termination series resistor at the amplifier's output will isolate the amplifier from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a backtermination resistor. Again, a small series resistor at the output can help to reduce peaking.
Choosing a Feedback Resistor
A feedback resistor is required to achieve unity gain; simply short the output pin to the inverting input pin. Gains greater than +1 require a feedback and gain resistor to set the desired gain. This gets interesting because the feedback resistor forms a pole with the parasitic capacitance at the inverting input. As the feedback resistance increases the
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455
Disable/Power-Down
The EL5152 and EL5253 can be disabled with their output placed in a high impedance state. The turn off time is about 330ns and the turn on time is about 130ns. When disabled, the amplifier's supply current is reduced to 17A typically; essentially eliminating power consumption. The amplifier's power down is controlled by standard TTL or CMOS signal levels at the ENABLE pin. The applied logic signal is relative to VS- pin. Letting the ENABLE pin float or the application of a signal that is less than 0.8V above VS- enables the amplifier. The amplifier is disabled when the signal at ENABLE pin is above VS+ -1.5V. For sinking:
n
PD MAX = V S x I SMAX +
( VOUTi - VS ) x ILOADi
i=1
Where: VS = Supply voltage ISMAX = Maximum quiescent supply current VOUT = Maximum output voltage of the application RLOAD = Load resistance tied to ground ILOAD = Load current N = number of amplifiers (Max = 2) By setting the two PDMAX equations equal to each other, we can solve the output current and RLOAD to avoid the device overheat.
Output Drive Capability
The EL5152 and EL5153 families do not have internal short circuit protection circuitry. Typically, short circuit currents as high as 95mA and 70mA can be expected and naturally, if the output is shorted indefinitely the part can easily be damaged from overheating, or excessive current density may eventually compromise metal integrity. Maximum reliability is maintained if the output current is always held below 40mA. This limit is set and limited by the design of the internal metal interconnect. Note that in transient applications, the part is extremely robust.
Power Supply Bypassing Printed Circuit Board Layout
As with any high frequency device, a good printed circuit board layout is necessary for optimum performance. Lead lengths should be as short as possible. The power supply pin must be well bypassed to reduce the risk of oscillation. For normal single supply operation, where the VS- pin is connected to the ground plane, a single 4.7F tantalum capacitor in parallel with a 0.1F ceramic capacitor from VS+ to GND will suffice. This same capacitor combination should be placed at each supply pin to ground if split supplies are to be used. In this case, the VS- pin becomes the negative supply rail. See Figure 1 for a complete tuned power supply bypass methodology.
Power Dissipation
With the high output drive capability of the EL5152 and EL5153 families, it is possible to exceed the 125C absolute maximum junction temperature under certain load current conditions. Therefore, it is important to calculate the maximum junction temperature for an application to determine if load conditions or package types need to be modified to assure operation of the amplifier in a safe operating area. The maximum power dissipation allowed in a package is determined according to:
T JMAX - T AMAX PD MAX = ------------------------------------------- JA
Printed Circuit Board Layout
For good AC performance, parasitic capacitance should be kept to minimum. Use of wire wound resistors should be avoided because of their additional series inductance. Use of sockets should also be avoided if possible. Sockets add parasitic inductance and capacitance that can result in compromised performance. Minimizing parasitic capacitance at the amplifier's inverting input pin is very important. The feedback resistor should be placed very close to the inverting input pin. Strip line design techniques are recommended for the signal traces.
Where: TJMAX = Maximum junction temperature TAMAX = Maximum ambient temperature JA = Thermal resistance of the package The maximum power dissipation actually produced by an IC is the total quiescent supply current times the total power supply voltage, plus the power in the IC due to the load, or: For sourcing:
n
PD MAX = V S x I SMAX +
i=1
( VS - VOUTi ) x ----------------R Li
V OUTi
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455 Application Circuits
Sullen Key Low Pass Filter
A common and easy to implement filter taking advantage of the wide bandwidth, low offset and low power demands of the EL5152. A derivation of the transfer function is provided for convenience. (See Figure 28.)
Sullen Key High Pass Filter
Again this useful filter benefits from the characteristics of the EL5152. The transfer function is very similar to the low pass so only the results are presented. (See Figure 29.)
5V V2 L1 10H R5 1K C6 1n C1 R1 1K V1 R2 1K C2 1n 2 1n 3 U1A + C3 1n
K = 1+ Vo = K
RB RA
1 V1 R2C2s + 1 Vo V1 - Vi Vo - Vi 1 + K - V1 + =0 1 R1 R2 C1s K H(s) = R1C1R2C2s 2 + ((1 - K )R1C1 + R1C2 + R21C2)s + 1 1 H( jw ) = 2 1 - w R1C1R2C2 + jw ((1 - K )R1C1 + R1C2 + R2C2) Holp = K wo = Q= 1 R1C1R2C2 1 R1C1 R1C2 R2C2 (1 - K ) + + R2C2 R2C1 R1C1
4 1 R7 VOUT 1K
V+ V-
11 1K RB RA 1K C5 1n R6 1K L3 10H 5V V3 C4 1n
Holp = K 1 RC 1 Q= 3 -K wo =
Equations simplify if we let all components be equal R=C
FIGURE 28. SULLEN KEY LOW PASS FILTER
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EL5152, EL5153, EL5252, EL5455
5V V2 L1 10H R5 1K C6 1n R8 C7 1n V1 C9 1n C2 1n 2 1K 3 U1A + V+ V-
C3 1n
Holp = K wo = 1 R1C1R2C2 1 R1C1 R1C2 R2C2 (1 - K ) + + R2C2 R2C1 R1C1
4 1 VOUT R7 1K
Q=
11 1K RB RA 1K C5 1n R6 1K L3 10H 5V V3 C4 1n
Holp =
K 4 -K
Equations simplify if we let all components be equal R=C
2 wo = RC Q= 2 4 -K
FIGURE 29. SULLEN KEY HIGH PASS FILTER
Differential Output Instrumentation Amplifier
The addition of a third amplifier to the conventional three amplifier Instrumentation Amplifier introduces the benefits of differential signal realization, specifically the advantage of using common mode rejection to remove coupled noise and ground-potential errors inherent in remote transmission. This configuration also provides enhanced bandwidth, wider output swing and faster slew rate than conventional three amplifier solutions with only the cost of an additional amplifier and few resistors.
e1
A1 + R2
R3
R3
A3 + R3 R3 +
eo3
RG
R3
R3
REF eo
R2
A4 + R3 R3
eo4
A2 e2 +
e o3 = - ( 1 + 2R 2 R G ) ( e 1 - e 2 ) e o = - 2 ( 1 + 2R 2 R G ) ( e 1 - e 2 ) 2f C1, 2 BW = ----------------A Di
e o4 = ( 1 + 2R 2 R G ) ( e 1 - e 2 )
A Di = - 2 ( 1 + 2R 2 R G )
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455
Strain Gauge
The strain gauge is an ideal application to take advantage of the moderate bandwidth and high accuracy of the EL5152. The operation of the circuit is very straight forward. As the strain variable component resistor in the balanced bridge is subjected to increasing strain its resistance changes resulting in an imbalance in the bridge. A voltage variation from the referenced high accuracy source is generated and translated to the difference amplifier through the buffer stage. This voltage difference as a function of the strain is converted into an output voltage.
5V V2 L1 10H R5 1K C6 VARIABLE SUBJECT TO STRAIN 1n
1K V5 0V R15 1K
C3 1n
R16 R14 1K
22 1K 22
4
R17 1K R18 1K
3 U1A + 2 1K RF -
4 1 VOUT (V1+V2+V3+V4) RL 1K
V+ V-
4
11
C12 1n R11 C11 1K L4 10H V4 5V 1n
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455 MSOP Package Outline Drawing
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455 SO Package Outline Drawing
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FN7385.4 October 3, 2005
EL5152, EL5153, EL5252, EL5455 SOT-23 Package Outline Drawing
NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at http://www.intersil.com/design/packages/index.asp
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation's quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com 16
FN7385.4 October 3, 2005

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